Load control device having a low-power mode

ABSTRACT

A load control device for control of the power delivered from an AC power source to an electrical load comprises a power supply and a microprocessor that is able to operate the load control device in a low-power mode. The load control device may further comprise at least one visual indicator controlled by the microprocessor to provide visual feedback, where the microprocessor illuminates the visual indicator when the load is on and to turns the visual indicator off when the load is off during the low-power mode. The load control device may comprise a communication circuit coupled to the microprocessor for transmitting and/or receiving digital messages the microprocessor cause the communication circuit to draw less current from the power supply during the low-power mode. The microprocessor may operate in the low-power mode if the magnitude of a voltage of the power supply drops below a predetermined threshold.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation-in-part application of commonly-assigned, co-pending U.S. patent application Ser. No. 12/369,395, filed Feb. 11, 2009, which is a continuation application of U.S. patent application Ser. No. 11/480,146, filed Jun. 30, 2006, now U.S. Pat. No. 7,546,473, issued Jun. 9, 2009, which claims priority from U.S. Provisional Patent Application No. 60/695,784, filed Jun. 30, 2005, all entitled DIMMER HAVING A MICROPROCESSOR-CONTROLLED POWER SUPPLY, the entire disclosures of which are hereby incorporated by reference.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a two-wire load control device, specifically a two-wire dimmer switch having a microprocessor and a power supply for generating a direct-current (DC) voltage for powering the microprocessor, where the microprocessor is able to operate the dimmer switch in a low-power mode.

2. Description of the Related Art

A conventional two-wire dimmer has two connections: a “hot” connection to an alternating-current (AC) power supply and a “dimmed hot” connection to the lighting load. Standard dimmers use one or more semiconductor switches, such as triacs or field effect transistors (FETs), to control the current delivered to the lighting load and thus to control the intensity of the light. The semiconductor switches are typically coupled between the hot and dimmed hot connections of the dimmer.

Smart wall-mounted dimmers may include a user interface typically having a plurality of buttons for receiving inputs from a user and a plurality of status indicators for providing feedback to the user. These smart dimmers typically include a microprocessor or other processing device for allowing an advanced set of control features and feedback options to the end user. An example of a smart dimmer is disclosed in commonly assigned U.S. Pat. No. 5,248,919, issued on Sep. 28, 1993, entitled LIGHTING CONTROL DEVICE, which is herein incorporated by reference in its entirety.

A simplified block diagram of a prior art two-wire dimmer 100 is shown in FIG. 1. The dimmer 100 has a hot terminal 102 connected to an AC voltage source 104 and a dimmed hot terminal 106 connected to a lighting load 108 (e.g., an incandescent lamp). The dimmer 100 employs a bidirectional semiconductor switch 110 coupled between the hot terminal 102 and the dimmed hot terminal 106, to control the current through, and thus the intensity of, the lighting load 108. The semiconductor switch 110 has a control input (or gate), which is connected to a gate drive circuit 112. The input to the gate will render the semiconductor switch 110 conductive or non-conductive, which in turn controls the power supplied to the lighting load 108. The gate drive circuit 112 provides control inputs to the semiconductor switch 110 in response to command signals from a microprocessor 114.

The microprocessor 114 receives user inputs from a plurality of buttons 116 and generates command signals to drive a plurality of light emitting diodes (LEDs) 118 for visual feedback to the user of the dimmer 100. A zero-crossing detect circuit 120 determines the zero-crossing points of the AC source voltage from the AC power supply 104. A zero-crossing is defined as the time at which the AC supply voltage transitions from positive to negative polarity, or from negative to positive polarity, at the beginning of each half-cycle. The zero-crossing information is provided as an input to the microprocessor 114. The microprocessor 114 generates the gate control signals to operate the semiconductor switch 110 to thus provide voltage from the AC power supply 104 to the lighting load 108 at predetermined times relative to the zero-crossing points of the AC waveform.

In order to provide a DC voltage V_(CC) to power the microprocessor 114 and other low-voltage circuitry, the dimmer 100 includes a cat-ear power supply 122. A cat-ear power supply draws current only near the zero-crossings of the AC source voltage and derives its name from the shape of the current waveform that it draws from the AC voltage source. Because the dimmer 100 only has two terminals 102, 106 (i.e., it is a two-wire dimmer), the power supply 122 must draw current through the connected lighting load 108. In order for the power supply 122 to be able to draw sufficient current, the semiconductor switch 110 must be non-conductive so that a sufficient voltage is available across the power supply. Thus, the semiconductor 110 cannot be turned on for the entire length of a half-cycle, even when the maximum voltage across the lighting load 108 is desired.

A simplified schematic diagram of the prior art cat-ear power supply 122 is shown in FIG. 2. The cat-ear power supply is provided on the DC-side of a bridge rectifier comprising diodes D202, D204, D206, D208, such that the cat-ear power supply is able to generate the DC voltage V_(CC). The DC voltage V_(CC) is produced across an energy storage capacitor C210 and has a magnitude that is appropriate to power the microprocessor 114 and other low-voltage circuitry (e.g., approximately 5V_(DC)). The side of the energy storage capacitor C210 that is connected to circuit common (i.e., the cathode) is also connected to an NPN transistor Q212 and a PNP transistor Q214. A zener diode Z216 and a diode D218 are provided in series between the DC voltage V_(CC) and the base of the transistor Q214. The forward voltage drop of the diode D218 is approximately the same as the emitter-base voltage of the transistor Q214. Accordingly, the magnitude of the DC voltage V_(CC) produced across the energy storage capacitor C210 is limited to approximately the same magnitude as the break-over voltage of the zener diode Z216, e.g., 5.1 volts.

The primary charging or energy-receiving circuit for the energy storage capacitor C210 is through the transistor Q212 and a current limiting resistor 8220. When transistor Q214 is conductive, a voltage is produced across a resistor R222, and thus the base-emitter junction of the transistor Q212, causing the transistor Q212 to conduct. A resistor 8224 maintains the base current needed to keep the transistor Q214 conductive.

When the voltage across the power supply 122 reaches a certain magnitude, a PNP transistor Q226 begins to conduct, causing the transistor Q214, and thus the transistor Q212, to stop conducting. A zener diode Z228 and a resistor 8230 are connected in series between the base of the transistor Q226 and the emitter of the transistor Q212. A resistor 8232 is connected across the base-emitter junction of the transistor Q226. The zener diode Z228 will begin to conduct when the voltage at the base of the transistor Q226 exceeds the break-over voltage of the zener diode (approximately 12V). When the voltage across the resistor 8232 exceeds the required emitter-base voltage of the transistor Q226, the transistor Q226 will begin to conduct. Thus, when an appropriate voltage (e.g., approximately 16V) is produced across the power supply 122, the transistor Q226 will begin to conduct, causing the transistors Q212, Q214 to stop conducting, thus halting the charging of the energy storage capacitor C210. A capacitor C234 is coupled across the resistor R232 to provide a time delay in the shut-off of the charging of the energy storage capacitor C210. When the voltage across the power supply 122 drops below the appropriate level (e.g., approximately 16V), the transistor Q226 stops conducting and the energy storage capacitor C210 is able to charge again.

The prior art cat-ear power supply 122 has some disadvantages. First, the period of time that the energy storage capacitor C210 is able to charge each half-cycle is set by the values of the chosen components of the power supply 122. If the power supply 122 is connected to an AC voltage source when the capacitor C210 is uncharged, the power supply is susceptible to drawing the initial charging current at the peak of the AC voltage, which can produce a very large current in the charging circuit of the power supply 122, especially through the transistor Q212 and the resistor R220. To prevent these parts from being damaged under this condition, the transistor Q212 and resistor R220 must be physically larger, more costly parts than would be required if only operating under normal conditions.

To ensure that the power supply 122 is able to draw enough current to maintain its output voltage at all times, the semiconductor switch 110 is turned off for at least a minimum off-time each half-cycle. The proper operation of the dimmer 100 is constrained by a number of worst-case operating conditions, such as high current draw by the low-voltage circuitry, worst-case line voltage input (i.e. when the AC power supply voltage is lower than normal), and worst-case load conditions (such as the number and the wattage of the lamps, the type of the lamps, and variations in the operating characteristics of the lamps). The wattage of the lighting load 108 is particularly important since the AC voltage source 104 is coupled across the power supply 122 and the lighting load in series, and thus, the impedance of the lighting load directly affects the voltage developed across the power supply and the time required to charge the power supply. The impedance of a lighting load will decrease as the rated wattage is increased, and vice versa. Thus, the worst-case time required to charge the power supply 122 occurs when a low-wattage lamp is connected to the dimmer 100 since the impedance of the load will be substantially higher and the voltage across the power supply will be substantially lower with this type of load. When considering the worst-case conditions, 40 W lamps are often used as the minimum load likely to be encountered.

By considering these worst-case conditions, the minimum off-time is determined by calculating the off-time that will guarantee that the power supply 122 will charge fully for even the worst-case conditions. The resulting off-time generally ends up being a significant portion of each half-cycle and constrains the maximum light level of the attached lighting load 108. However, these worst-case conditions are often not encountered in practice. Under typical conditions, the semiconductor switch could be rendered conductive for a greater amount of time during each half-cycle in order to conduct current to the load for a greater amount of time. Accordingly, the lighting load 108 will reach a higher intensity that is closer to the intensity achieved when the full line voltage is provided to the load.

Some prior art dimmers have held the minimum off-time constant under all conditions, and thus have suffered from a smaller dimming range than would otherwise be possible. Another prior art two-wire dimmer 300, which is shown in FIG. 3, monitors the internal power supply and decreases conduction time of the semiconductor switch, if needed. The two-wire dimmer 300 is able to provide the maximum possible light intensity at high-end while simultaneously ensuring sufficient charging time for proper operation of an internal power supply, and hence, the dimmer. The dimmer 300 is described in greater detail in co-pending U.S. Pat. No. 7,242,150, issued Jul. 10, 2007, entitled DIMMER HAVING A POWER SUPPLY MONITORING CIRCUIT, which is incorporated herein by reference in its entirety.

Referring to FIG. 3, the two-wire dimmer 300 has two connections: a hot terminal 302 to an AC power supply 304 and a dimmed hot terminal 306 to a lighting load 308. To control the AC voltage delivered to the lighting load 308, two field-effect transistors (FETs) 310A, 310B are provided in anti-serial connection between the hot terminal 302 and the dimmed hot terminal 306. The first FET 310A conducts during the positive half-cycle of the AC waveform and the second FET 310B conducts during the negative half-cycle of the AC waveform. The conduction state of the FETs 310A, 310B is determined by a microprocessor 314 that interfaces to the FETs through a gate drive circuit 312. The dimmer 300 also includes a plurality of buttons 316 for input from a user and a plurality of LEDs 318 for visual feedback to the user. The microprocessor 314 determines the appropriate dimming level of the lighting load 308 from the inputs from the buttons 316. A zero-crossing detect circuit 320 receives the AC supply voltage through diode 321A in the positive half-cycles and through diode 321B in the negative half-cycles and provides a control signal to the microprocessor 314 that identifies the zero-crossings of the AC supply voltage.

The dimmer 300 further includes a power supply 322 to power the microprocessor 314 and the other low-voltage circuitry. The power supply 322 is only able to charge when the FETs 310A, 310B are both turned off (i.e., they are non-conducting) and there is a sufficient voltage potential across the dimmer. The power supply 322 is coupled to an input capacitor 324 and an output capacitor 326. The output capacitor 326 holds the output of the power supply V_(CC) at a substantially constant DC voltage to provide power for the microprocessor 314. The input of the power supply 322 is coupled to the hot terminal 302 and the dimmed hot terminal 306 through the two diodes 321A, 321B, such that the input capacitor 324 charges during both the positive and negative half-cycles.

The dimmer 300 also includes a voltage divider that comprises two resistors 328, 330 and is coupled between the input of the power supply 322 and circuit common. The voltage divider produces a sense voltage V_(S) at the junction of the two resistors 328, 330. The sense voltage V_(S) is provided to the microprocessor 314 to monitor the voltage level at the input of the power supply 322. The microprocessor 314 preferably includes an analog-to-digital converter (ADC) for sampling the value of the sense voltage V_(S). The microprocessor 314 monitors the sense voltage V_(S) and decreases the conduction times of the FETs 310A, 310B when the sense voltage V_(S) drops below a first predetermined voltage threshold V₁. Further, the microprocessor 314 increases the conduction times of the FETs 310A, 310B when the sense voltage then rises above a second predetermined voltage threshold V₂, greater than the first threshold V₁. Alternatively, if the microprocessor does not include an ADC, the dimmer 100 could include a hardware comparison circuit, including one or more comparator integrated circuits, to compare the sense voltage with the first and second voltage thresholds and then provide a logic signal to the microprocessor 314.

By monitoring the input of the power supply 322, the microprocessor 314 of the dimmer 300 is able to determine when the input voltage has dropped to a level that is inappropriate for continued charging of the input capacitor 324. For example, if the sense voltage V_(S) falls below the first voltage threshold V₁, then the capacitor 324 needs a greater time to properly charge and the on-times of the FETs 310A, 310B are decreased. On the other hand, if the sense voltage V_(S) remains above the first voltage threshold V₁, the input capacitor 324 is able to properly charge each half-cycle.

Thus, the microprocessor 314 continuously monitors the voltage on the input capacitor 324 and automatically decreases the conduction times of the FETs 310A, 310B when the voltage falls to a level that will not guarantee proper operation of the power supply 322. The dimmer 300 is able to provide the maximum possible conduction times of the FETs 310A, 310B at high end (i.e., maximum light intensity) while simultaneously ensuring sufficient charging time for proper operation of the power supply 322.

However, the dimmer 300 of FIG. 3 requires that the microprocessor 314 include an ADC or that a hardware comparison circuit be included between the power supply 322 and the microprocessor. Also, the dimmer 300 is not able to control the power supply 322 directly, but operates the FETs 310A, 310B in order to indirectly control the time during which the power supply draws current.

Thus, there exists a need for a simple cat-ear power supply for a dimmer that is operable to be monitored and directly controlled by a microprocessor, specifically to control the time period that the power supply draws current and to control the conduction time of the semiconductor switch in response to the operation of the power supply, without the need for an ADC or a complex hardware comparison circuit.

SUMMARY OF THE INVENTION

According to an embodiment of the present invention, a load control device for control of the power delivered from an AC power source to an electrical load comprises: (1) a controllably conductive device adapted to be coupled between the AC power source and the electrical load for controlling the power delivered to the load; (2) a microprocessor coupled to the controllably conductive device for controlling the controllably conductive device; (3) at least one visual indicator controlled by the microprocessor to provide visual feedback; and (4) a power supply adapted to draw current from the AC power source through the electrical load for generating a DC voltage across an energy storage capacitor for powering the microprocessor and the visual indicator. The microprocessor is able to operate the load control device in a low-power mode during which the microprocessor illuminates the visual indicator when the load is on and to turns the visual indicator off when the load is off.

According to another embodiment of the present invention, a load control device for control of the power delivered from an AC power source to an electrical load comprises: (1) a controllably conductive device adapted to be coupled between the AC power source and the electrical load for controlling the power delivered to the load; (2) a microprocessor coupled to the controllably conductive device for controlling the controllably conductive device; (3) a communication circuit coupled to the microprocessor for transmitting and/or receiving digital messages; and (4) a power supply adapted to draw current from the AC power source through the electrical load for generating a DC voltage across an energy storage capacitor for powering the microprocessor and the communication circuit. The microprocessor is able to operate the load control device in a low-power mode during which the microprocessor causes the communication circuit to draw less current from the energy storage capacitor.

According to another embodiment of the present invention, a load control device for control of the power delivered from an AC power source to an electrical load comprises: (1) a controllably conductive device adapted to be coupled between the AC power source and the electrical load for controlling the power delivered to the load; (2) a microprocessor coupled to the controllably conductive device for controlling the controllably conductive device; (3) a power supply adapted to draw current from the AC power source through the electrical load for generating a DC voltage across an energy storage capacitor for powering the microprocessor and the LED; and (4) a load circuit drawing current from the energy storage capacitor of the power supply. The microprocessor is operable to cause the load circuit to draw less current if the magnitude of a voltage of the power supply drops below a predetermined threshold.

Other features and advantages of the present invention will become apparent from the following description of the invention that refers to the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a simplified block diagram of a prior art two-wire dimmer;

FIG. 2 is a simplified schematic diagram of a cat-ear power supply of the dimmer of FIG. 1;

FIG. 3 is a simplified block diagram of another prior art two-wire dimmer;

FIG. 4 is a simplified block diagram of a two-wire dimmer according to the present invention;

FIG. 5A is a simplified schematic diagram of a cat-ear power supply according to the present invention;

FIG. 5B is a simplified schematic diagram of a cat-ear power supply including a half-wave rectifier bridge according to the present invention;

FIG. 5C is a simplified schematic diagram of a cat-ear power supply including a transistor in series with a boot-strap resistor according to the present invention;

FIG. 6A shows a flowchart of the normal operation process of a microprocessor of the dimmer of FIG. 4;

FIG. 6B shows a flowchart of a power supply control/monitor routine of the process of FIG. 6A;

FIG. 6C shows a flowchart of a dimming range control routine of the process of FIG. 6A; and

FIG. 7 shows a flowchart of the startup routine of the microprocessor of the dimmer of FIG. 4.

DETAILED DESCRIPTION OF THE INVENTION

The foregoing summary, as well as the following detailed description of the preferred embodiments, is better understood when read in conjunction with the appended drawings. For the purposes of illustrating the invention, there is shown in the drawings an embodiment that is presently preferred, in which like numerals represent similar parts throughout the several views of the drawings, it being understood, however, that the invention is not limited to the specific methods and instrumentalities disclosed.

FIG. 4 is a simplified block diagram of a two-wire dimmer 400 according to the present invention. The dimmer 400 includes many similar blocks as the dimmer 100 of FIG. 1, which have the same function as described previously. However, those components of the dimmer 400 that differ from the prior art dimmer 100 will be described in greater detail below.

The dimmer 400 includes a controllably conductive device, e.g., a bidirectional semiconductor switch 410, that is adapted to be coupled in series electrical connection between an AC power source 404 and a lighting load 408. The bidirectional semiconductor switch 410 may be implemented as, for example, a triac, a field effect transistor (FET) or an insulated gate bipolar transistor (IGBT) in a bridge rectifier, two FETs or IGBTs in anti-series connection, or any other suitable type of semiconductor switch. The dimmer 400 further comprises a microprocessor 414 for driving the bidirectional semiconductor switch 410 via a gate drive circuit 412. The microprocessor 414 may be implemented as any suitable controller, such as, for example, a programmable logic device (PLD), a microcontroller, an application specific integrated circuit (ASIC), or a field programmable gate array (FPGA).

The microprocessor 414 receives inputs from a zero-crossing detector circuit 420 and a plurality of buttons 416 and controls a plurality of LEDs 418. The microprocessor 414 is operable to illuminate one of the LEDs 418 brightly to a first intensity. When the lighting load 108 is off, the microprocessor 414 may illuminate the LEDs 418 dimly to a second intensity less than the first intensity to provide a nightlight feature. One of the LEDs 418 may be illuminated to a third intensity (between the first and second intensities) to display a target intensity to which the microprocessor 414 will control the lighting load 108 when the lighting load is turned back on. The nightlight feature is described in greater detail in commonly-assigned U.S. Pat. No. 5,399,940, issued Mar. 21, 1995, entitled LIGHTING INDICATING DEVICE HAVING PLURAL ILLUMINATING ELEMENTS WITH ALL SUCH ELEMENTS BEING ILLUMINATED WITH ONE BEING GREATER THAN THE OTHERS, the entire disclosure of which is hereby incorporated by reference

A cat-ear power supply 422 generates a DC voltage V_(CC) for powering the microprocessor 414. The microprocessor 414 is coupled to the cat-ear power supply through a port 424 and is operable to monitor the status of the power supply (i.e., whether the power supply is fully charged) and to control the operation of the power supply.

The dimmer 400 also includes a communication circuit 426 to transmit and receive messages with other control devices in a lighting control system. The communication circuit 426 is coupled to a communications link, for example, a wired serial control link, a power-line carrier (PLC) communication link, or a wireless communication link, such as an infrared (IR) or a radio frequency (RF) communication link. For example, the communication circuit 426 may comprise an RF communication circuit (e.g., an RF transmitter, an RF receiver, or an RF transceiver) for transmitting and/or receiving RF signals. The microprocessor 414 may be operable to control the bidirectional semiconductor switch 410 in response to the digital messages received via the RF signals. The RF communication circuit is able to be put in a sleep mode (i.e., low-power mode) to conserve power. During the sleep mode, the RF communication circuit is operable to wake up periodically to sample (e.g., listen) for RF energy at a sampling period T_(SAMPLE). Each time that the RF transceiver wakes up, additional power is consumed by the RF transceiver (since the RF transceiver is fully powered when awake).

Examples of RF load control devices are described in greater detail in commonly-assigned U.S. Pat. No. 5,982,103, issued Nov. 9, 1999, and U.S. Pat. No. 7,362,285, issued Apr. 22, 2008, both entitled COMPACT RADIO FREQUENCY TRANSMITTING AND RECEIVING ANTENNA AND CONTROL DEVICE EMPLOYING SAME, and U.S. patent application Ser. No. 13/415,537, filed Mar. 8, 2012, entitled LOW-POWER RADIO-FREQUENCY RECEIVER, the entire disclosures of which are hereby incorporated by reference. An example of an IR lighting control system is described in commonly assigned U.S. Pat. No. 6,300,727, issued Oct. 9, 2001, entitled LIGHTING CONTROL WITH WIRELESS REMOTE CONTROL AND PROGRAMMABILITY, the entire disclosure of which is hereby incorporated by reference.

FIG. 5A is a simplified schematic diagram of the cat-ear power supply 422 according to the present invention. The cat-ear power supply 422 is provided inside of a full-wave bridge rectifier comprising diodes D502, D504, D506, D508, such that the cat-ear power supply is able to produce a DC voltage V_(CC) across an energy storage element, for example, an energy storage capacitor C510. The rectifier bridge allows the cat-ear power supply 422 to draw current in both half-cycles of the AC source voltage. The energy storage capacitor preferably has a capacitance of approximately 680 μF.

Alternatively, the cat-ear power supply 422 could include a half-wave bridge rectifier, for example, comprising only diode D508, i.e., the diodes D502, D504, D506 would not be provided, as shown in FIG. 5B. The half-wave rectifier bridge comprising only one diode D508 would allow the cat-ear power supply 422 to charge in only the positive or the negative half-cycles and thus only once per line cycle.

The cat-ear power supply 422 includes a passive charging or energy-receiving circuit comprising a “boot-strap” resistor R512. The resistor R512 allows the energy storage capacitor C510 to begin charging before the microprocessor 414 is powered up and running, such that the energy storage capacitor C510 is only charged by the current flowing through the resistor R512 and the impedance of the lighting load 408. The resistor R512 preferably has a resistance of 151 a which is suitably low enough to ensure sufficient current is available to bring the microcontroller out of the internal low-voltage reset mode. The current through the resistor R512 provides sufficient charge on the energy storage capacitor C510 to bring the microprocessor 414 out of an internal low-voltage reset mode (e.g., when voltage supply input to the microprocessor rises above approximately 3.75V). During the time when the energy storage capacitor C510 is charging through the boot-strap resistor R512, the majority of the current drawn from the power supply 422 (i.e., drawn by the microprocessor 414 and the other low-voltage circuitry) is minimal since the microprocessor is unpowered or in reset mode. The energy storage capacitor C510 charges through the boot-strap resistor R512 until the microprocessor 414 is running and able to control the power supply 422. The boot-strap resistor R512 is also sized to be suitably large enough in impedance so that during normal operation, the power dissipation of the resistor is minimized.

Once powered, the microprocessor 414 can enable an active charging or energy-receiving circuit for the energy storage capacitor C510 through an NPN transistor Q514 (e.g., part number MJD47T4 manufactured by On Semiconductor) and a resistor R516. The resistor R516 has a low resistance (preferably 12Ω), which provides a charging current through the energy storage capacitor C510 of a much greater magnitude than the charging current through the passive charging circuit comprising the resistor R512, thus allowing the energy storage capacitor C510 to charge at a greater rate, i.e., with a smaller time constant. The microprocessor 414 is coupled to the base of a PNP transistor Q518 (e.g., part number MMBTA92 manufactured by On Semiconductor) through a resistor R520 (preferably having a resistance of 4.7 kΩ). When the energy storage capacitor C510 is charging through the resistor R512 during start up, the port 424 of the microprocessor 414 that is connected to the resistor R520 is maintained as a high impedance and the transistor Q514 is non-conductive.

Upon coming out of reset mode, the microprocessor 414 measures the frequency of, and synchronizes to, the AC voltage supply 404 by means of the zero-crossing detect circuit 420 and the internal clock of the microprocessor. After synchronizing with the AC voltage supply 404, the microprocessor 414 can enable the active charging circuit by pulling the port 424 low and thereby pulling down the base of the transistor Q518. Thus, a voltage is produced across a resistor R522 and the emitter-base junction of the transistor Q518 allowing current flow through the transistor Q518 and an emitter resistor R524. The resistors R522, R524 preferably have resistances of 10 kΩ and 510Ω, respectively. The current flow through the transistor Q518 produces a voltage across a resistor R526 coupled across the base-emitter junction of the transistor Q514 and provides base current for the transistor Q514. This enables the active charging circuit of the energy storage capacitor C510, allowing the charging current for the energy storage capacitor C510 to flow through the transistor Q514 and the resistor R516. The current through the transistor Q514 is limited by the resistor R516 and a zener diode Z528 (preferably having a break-over voltage of 3.3V, e.g., part number MMSZ4684ET1 manufactured by On Semiconductor). A capacitor C530 is coupled across the resistor R526 and provides some time delay in the enabling of the active charging circuit. Preferably, the resistor R526 has a resistance of 10 kΩ and the capacitor C530 has a capacitance of 0.33 μF.

The power supply 422 further includes a hardware shut-off circuit having a PNP transistor Q536, a resistor R532, and a zener diode Z534. The resistor R532 (preferably having a resistance of 1 kΩ) and the zener diode Z534 are coupled in series across the energy storage capacitor C510, with the anode of the zener diode connected to circuit common. The PNP transistor Q536 (e.g., part number MBT3906DW1T1 manufactured by On Semiconductor) is coupled between the DC voltage V_(CC) and the base of the transistor Q518. The base of the transistor Q536 is connected to the junction of the resistor R532 and the zener diode Z534. The zener diode Z534 preferably has a break-over voltage of 4.7V (e.g., part number MMSZ4688ET1 manufactured by On Semiconductor), such that when the voltage across the energy storage capacitor C510 reaches approximately 5.2V (i.e., the DC voltage V_(CC) is at an appropriate level), current will flow through the zener diode Z534 and the resistor R532, producing a voltage across the resistor. Thus, the transistor Q536 will begin to conduct, pulling the base of the transistor Q518 up to the DC voltage V_(CC). This overrides the control signal from the port 424 of the microprocessor 414 and disables the active charging circuit through the transistor Q514 and the resistor R516.

The microprocessor 414 is operable to monitor the voltage at the base of the transistor Q518 to determine if the energy storage capacitor C510 has fully charged. By briefly changing the port 424 from being configured as an output to being configured as an input, the microprocessor 414 can periodically check to see if the base of the transistor Q518 is being pulled up to the DC voltage V_(CC) by the transistor Q536. A capacitor C538 is provided from the DC voltage V_(CC) to the base of the transistor Q518 and preferably has a capacitance of 0.01 g. During the times that the port 424 has been changed to an input to monitor the power supply 422, the capacitor C538 holds the voltage at the base of the transistor Q518 at a level appropriate to keep the transistor Q518 in the conductive state if the charging of the energy storage capacitor C510 has not yet finished.

The microprocessor 414 is adapted to control the time period when the active charging circuit through the transistor Q514 is enabled each half-cycle of the AC voltage source 404. In order to limit this charging time to the beginning portion of each half-cycle, the microprocessor 414 only enables the active charging circuit at a predetermined time after a zero-crossing has been detected by the zero-crossing detect circuit 420. In this way, the active charging circuit is never enabled when the AC voltage is at its peak value. Accordingly, the transistor Q514 and the resistor R516 are never operated outside of their safe operating area, and do not need to be large, expensive parts as were required in the prior art cat-ear power supply 122 of FIG. 2.

In response to the time that is required to charge the power supply 422, the microprocessor 414 is operable to change the dimming range of the dimmer. By default, the dimmer 400 begins operating with a normal dimming range that has been determined by considering worst-case line conditions and load conditions. For example, the worst-case load condition for the power supply 422 assumes a 40 W lamp as the lighting load. The microprocessor 414 can change the dimming range of dimmer 400 to a maximum dimming range to provide a greater high-end intensity of the attached lighting load than the normal dimming range. The microprocessor 414 can also change the dimming range back to the normal dimming range in response to operating conditions.

The microprocessor 414 preferably includes a timer such that the microprocessor is able to record the time required to charge the power supply 422 each half-cycle. The microprocessor records the time from when the active charging circuit is enabled to when the port 424 is pulled high by the transistor Q536 of the hardware shut-off circuit. If this time is below a predetermined threshold for a number of consecutive half-cycles, it is assumed that the energy storage capacitor C510 is easily able to charge each half-cycle and the microprocessor 414 is programmed to increase the dimming range of the dimmer 400 to the maximum dimming range, such that the high-end has a greater intensity. Since the average current draw of the power supply 422 is greatly dependent on the impedance of the connected lighting load, the dimmer 400 will generally tend to continue operating with either the normal dimming range or the maximum dimming range, without changing between the ranges, until the connected lighting load is changed to a different wattage. Since the load impedance changes as the dimmer 400 changes the intensity of the lighting load 408 (i.e., as the light level is increased, the impedance of the lighting load will increase), the microprocessor 414 preferably monitors the time required to charge the energy storage capacitor C510 at or near high-end since this is when the power supply 422 will draw the worst-case charging current.

The microprocessor 414 is also capable of disabling the active charging circuit by pulling the port 424 high before the hardware shut-off circuit disables the active charging circuit. If a predetermined time elapses (from when the active charging circuit is enabled) before the transistor Q536 shuts off the active charging circuit, the microprocessor 414 will preferably override the hardware shut-off circuit to protect the transistor Q514 and the resistor R516 from potential damage, i.e., as the voltage across the dimmer increases, the current through, and the power dissipation of, the transistor Q514 and the resistor R516 will increase. The predetermined time preferably corresponds to a time after which the voltage across the dimmer is great enough to pose a potential hazard to the susceptible parts of the power supply 422, i.e., the transistor Q514 and the resistor R516. The energy storage capacitor C510 can potentially require greater amounts of time to charge: (1) during startup of the power supply 422; (2) if the power requirements of the microprocessor 414 and other low-voltage circuitry are greater than normal; or (3) if the energy storage capacitor is not able to charge during a certain half-cycle.

The microprocessor 414 is also able to control the loads of the power supply 422, i.e., the gate drive circuit 412, the LEDs 418, and the communication circuit 426 (i.e., load circuits). If the microprocessor 414 detects that the energy storage capacitor C510 does not have enough time to charge during each half-cycle, the microprocessor 414 can optionally cause some of the loads of the power supply to draw less current by, for example, turning off or dimming the LEDs 418, turning off the semiconductor switch 410, disabling the communication circuit 426, or placing the communication circuit in an idle mode. Alternatively, the microprocessor 414 could increase the sampling period T_(SAMPLE), such that the RF communication circuit wakes up less often to sample for RF energy and thus consumes less power. Also, during the startup of the power supply 422, the microprocessor 414 does not enable the loads of the power supply until after a predetermined number of half-cycles to allow the DC voltage V_(CC) provided by the energy storage capacitor C510 to achieve a stable value.

The power supply 422 may also include an additional semiconductor switch, for example, a NPN transistor Q540 (as shown in FIG. 5C), for selectively switching the boot-strap resistor R512 out of the circuit after startup of the power supply, i.e., when the boot-strap resistor is no longer needed. The base of the transistor Q540 is coupled to an output port 542 of the microprocessor 414 through a resistor R544. Accordingly, the microprocessor 414 is operable to render the transistor Q540 non-conductive to disable the passive energy-receiving circuit comprising the boot-strap resistor R512. The base of the transistor Q540 is also coupled to a resistor R546. Before the microprocessor 414 is powered, a current flows through the resistor R546 into the base of the transistor Q540, such that the transistor Q540 allows the energy storage capacitor C510 to charge through the boot-strap resistor R512.

FIG. 6A shows a flowchart of the normal operation process of the microprocessor 414 for controlling the power supply 422 of the dimmer 400. This process is performed each half-cycle. The process begins each half-cycle at a zero-crossing of the AC voltage at step 600, and then executes in sequence a power supply control/monitor routine 602 and a dimming range control routine 604.

FIG. 6B shows a flowchart of the power supply control/monitor routine 602 in greater detail. At step 605, a “turn-on” timer is initialized, for example, to 150 μsec, and is started in a decrementing operation. The turn-on timer determines the time between a zero-crossing and when the active charging circuit is enabled. If the turn-on timer has not elapsed (i.e., has not decreased to zero) at step 606, the process loops until the turn-on timer has elapsed, at which time a “turn-off” timer is started at step 608 and decreases in value with respect to time. The turn-off timer is initialized, for example, to 400 μsec, and is used to override the hardware shut-off circuit comprising transistor Q536 if the energy storage capacitor C510 does not charge fully before the turn-off timer elapses (i.e., decreases to zero).

At step 610, port 424 of the microprocessor 414 is configured as an output, and then, the port 424 is pulled low at step 612, thus enabling the active charging circuit and causing the energy storage capacitor C510 to begin charging (i.e., storing energy) at a greater rate, i.e., with a smaller time constant. Next, the microprocessor waits for a time t_(WAIT) (which is preferably 100 μsec to 200 μsec) at step 614. Now, the microprocessor 414 checks the voltage at the port 424 by first configuring the port as an input at step 616 and then reading the port at step 618. The voltage at the port 424 will either be low (i.e., at or about zero volts) if the energy storage capacitor C510 has not finished charging, or high (i.e., at or about V_(CC)) if the energy storage capacitor C510 is sufficiently charged and the transistor Q536 is conducting. Since the microprocessor 414 can only cease driving the port 424 for short, infrequent periods of time to prevent disabling the active charging circuit, the wait operation at step 614 allows the microprocessor 414 to periodically monitor the voltage at port 424 at an appropriate interval of time.

At step 620, if the port 424 is high, then the turn-off timer is stopped at step 622, the port 424 is configured as an output at step 624, and the port is pulled high at step 626. The process then exits. If at step 620 the port 424 is still low, a determination is made at step 628 as to whether the turn-off time has expired. If not, the process loops around to enable the active charging circuit and then to monitor the port 424 again. If the turn-off timer has expired at step 628, the active charging circuit is enabled at steps 624 and 626 and then the process exits.

FIG. 6C shows a flowchart of the dimming range control routine 604 in greater detail. At step 630, a charging time, t_(CHARGE), of the power supply 422 for the present half-cycle is determined from the final value of the turn-off timer. For example, if the original value of the turn-off timer is 400 μsec and the final value of the turn-off timer is 150 μsec, the charging time t_(CHARGE) is 250 μsec. If at step 632, the charging time t_(CHARGE) is less than a threshold, t_(TH), then the microprocessor 414 attempts to change the dimmer 400 to the maximum dimming range. If the charging time t_(CHARGE) is above the threshold t_(TH) at step 632, the microprocessor 414 will attempt to change the dimmer 400 to the normal dimming range. A variable K and a variable M are used to count the number of consecutive half-cycles that the charging time t_(CHARGE) is below the threshold t_(TH), or above the threshold t_(TH), respectively. Note that the variables K and M are preferably initialized to zero. The variables K and M are incremented until the variables reach maximum values, K_(MAX) and M_(MAX), respectively. Preferably, the maximum values K_(MAX) and M_(MAX) are both 3.

At step 634, if the variable M is greater than zero (i.e., the charging time t_(CHARGE) was above the threshold t_(TH) during the previous half-cycle), then the variable M is reset to zero (i.e., M equals zero) at step 636 and the variable K is incremented by one at step 638. If the variable M is not greater than zero at step 634, the process simply moves to step 638. If the variable K is equal to K_(MAX) at step 640, the charging time t_(CHARGE) has been above the threshold t_(TH) for the appropriate number of consecutive times and the dimming range is accordingly changed to the maximum dimming range at step 642. However, if the variable K is not equal to K_(MAX) at step 640, the dimming range is not changed and the process exits.

If the charging time t_(CHARGE) is above the threshold t_(TH) at step 632, the microprocessor 414 uses a similar process in steps 644, 646, 648, 650 to determine if the dimmer 400 should change to the normal dimming range at step 652.

FIG. 7 shows a flowchart of the startup routine of the microprocessor 414. The process begins when the microprocessor comes out of reset mode at step 702. At step 704, the microprocessor 414 maintains the port 424 at high impedance to keep the active charging circuit through transistor Q514 disabled. The microprocessor 414 measures the frequency of the AC source voltage and synchronizes to this frequency at step 706. At step 708, the variables K and M (that are used in the dimming range control routine 604) and a variable ZC_CNT are initialized to zero. The variable ZC_CNT is used by the startup routine to count the zero-crossings of the AC voltage supply 404 after startup.

Next, the microprocessor 414 executes the power supply control/monitor routine 602 (as shown in FIG. 6B) for a number, ZC_(MAX), of consecutive half-cycles to allow the power supply 422 to regulate the voltage across the energy storage capacitor C510 to a specified level. At step 710, the process waits until a zero-crossing is detected, and then the power supply control/monitor routine 602 is executed. At step 712, if the variable ZC_CNT is less than or equal to the number ZC_(MAX), then the variable ZC_CNT is incremented by one at step 714 and the process loops to wait for the next zero-crossing at step 710. If the variable ZC_CNT is greater than the number ZC_(MAX) at step 656, the microprocessor 414 then begins driving the semiconductor switch 410 to provide power to the lighting load 408, turns on the LEDs 418, and begins communicating via the communication circuit 426 at step 716. Next, the startup routine exits.

While the present invention has been primarily discussed operating in a closed loop mode in which the microprocessor 414 is able to monitor the power supply 422, the microprocessor may also operate in an open loop mode. The microprocessor 414 could simply turn on (i.e., enable) the active charging circuit each half-cycle and allow the hardware shut-off circuit to turn off (i.e., disable) the active charging circuit. Alternatively, the microprocessor 414 could turn off the active charging circuit of the power supply 422 at a predetermined time after the active charging circuit is turned on, rather than monitoring the power supply in order to turn off the active charging circuit.

In addition, the microprocessor 414 may alternatively be operable to monitor the magnitude of a voltage of the power supply 422 to determine if the capacitor C510 has enough time to sufficiently charge rather than measuring the time required to charge the capacitor C510 each half-cycle and determining if the time required to charge the capacitor C510 is below a predetermined threshold for a number of consecutive half-cycles. For example, the microprocessor 414 may monitor the DC voltage V_(CC) across the capacitor C510 or another operating voltage of the power supply 422. The microprocessor 414 is operable to cause the loads of the power supply 422 (i.e., the gate drive circuit 412, the LEDs 418, and the communication circuit 426) to draw less current if the magnitude of the DC voltage V_(CC) across the capacitor C510 of the power supply drops below a predetermined threshold.

While the present invention has been described with reference to the lighting load 108 (shown as an incandescent lamp in FIG. 1), the lighting load could also comprise other types of lighting loads, such as, for example, screw-in light-emitting diode (LED) light sources having integral LED drivers, screw-in compact fluorescent lamps having integral ballast circuits, halogen lamps, electronic low-voltage lighting loads, and magnetic low-voltage lighting loads, and other types of electrical loads, such as, for example, motor loads. In addition, the concepts of the present invention could be applied to an electronic switch for simply toggling an electrical load on and off.

With some types of lighting loads, such as the screw-in LED light sources and the screw-in compact fluorescent lamps, the magnitude of the charging current of the power supply 422 conducted through the load may be great enough to cause either the LED driver or the ballast circuit to illuminate the controlled LED light source or fluorescent lamp to a level that is perceptible by the human eye when the light source should be off. Accordingly, the microprocessor 414 may be operable to cause the dimmer 400 enter a low-power mode in response to a user executing an advanced programming mode of the dimmer, i.e., in response to one or more actuations of the buttons 416. In the low-power mode, the microprocessor 414 may disable one or more of the loads of the power supply 422 (i.e., the gate drive circuit 412, the LEDs 418, and the communication circuit 426) to decrease the magnitude of the current conducted through the lighting load 108 when the lighting load is off. For example, the microprocessor 414 may be operable to turn off the LEDs 418, such that the dimmer 400 does not provide the nightlight feature when the lighting load 108 is off. Further, the microprocessor 414 may be operable to disable the RF communication circuit when the lighting load 108 is off, for example, by controlling an enable pin of an integrated circuit (IC) of the RF communication circuit or by rendering non-conductive a controllable switch (e.g., a transistor) that is electrically coupled between the DC voltage V_(CC) and the RF communication circuit. Alternatively, the microprocessor 414 could increase the sampling period T_(SAMPLE), such that the RF communication circuit wakes up less often to sample for RF energy and thus consumes less power.

Although the word “device” has been used to describe the load control device of the present invention and the elements of the load control device, it should be noted that each “device” described herein need not be fully contained in a single enclosure or structure. For example, the dimmer 400 may comprise a plurality of buttons in a wall-mounted enclosure and a processor that is included in a separate location. Also, one “device” may be contained in another “device”.

Additionally, the circuit diagrams shown in the figures and described in the text are an example of the invention and are not the only implementations possible. As appreciated by a person of ordinary skill in the art, component, software, and circuit substitutions and alterations may be made to the present invention without limitation except as identified by the appended claims.

Although the present invention has been described in relation to particular embodiments thereof, many other variations and modifications and other uses will become apparent to those skilled in the art. It is preferred, therefore, that the present invention be limited not by the specific disclosure herein, but only by the appended claims. 

What is claimed is:
 1. A load control device for control of the power delivered from an AC power source to an electrical load, the load control device comprising: a controllably conductive device adapted to be coupled between the AC power source and the electrical load for controlling the power delivered to the load; a microprocessor coupled to the controllably conductive device for controlling the controllably conductive device; at least one visual indicator controlled by the microprocessor to provide visual feedback; and a power supply adapted to draw current from the AC power source through the electrical load for generating a DC voltage across an energy storage capacitor for powering the microprocessor and the visual indicator; wherein the microprocessor is able to operate the load control device in a low-power mode during which the microprocessor illuminates the visual indicator when the load is on and turns the visual indicator off when the load is off.
 2. The load control device of claim 1, further comprising: a button for receiving a user input; wherein the control circuit is able to operate the load control device in the low-power mode in response to an actuation of the button.
 3. The load control device of claim 2, wherein the microprocessor is operable to cause the load control device to enter the low-power mode using an advanced programming mode of the load control device.
 4. The load control device of claim 1, wherein the load circuit comprises a plurality of visual indicators controlled by the microprocessor to provide visual feedback; wherein the microprocessor is operable to illuminate at least one of the visual indicators when the load is on and to turn off all of the visual indicators when the load is off when operating in the low-power mode.
 5. The load control device of claim 1, wherein, when not in the low-power mode, the microprocessor is operable to illuminate the visual indicator to a first intensity when the load is on and to illuminate the visual indicator to a second intensity less than the first intensity when the load is off.
 6. The load control device of claim 1, wherein the load control device comprises a dimmer for controlling the power delivered to a lighting load.
 7. The load control device of claim 1, wherein the power supply comprises a transistor for controllably storing energy in the energy storage capacitor, the microprocessor operatively coupled to the transistor for controlling the transistor.
 8. A load control device for control of the power delivered from an AC power source to an electrical load, the load control device comprising: a controllably conductive device adapted to be coupled between the AC power source and the electrical load for controlling the power delivered to the load; a microprocessor coupled to the controllably conductive device for controlling the controllably conductive device; a communication circuit coupled to the microprocessor for transmitting and/or receiving digital messages; and a power supply adapted to draw current from the AC power source through the electrical load for generating a DC voltage across an energy storage capacitor for powering the microprocessor and the communication circuit; wherein the microprocessor is able to operate the load control device in a low-power mode during which the microprocessor causes the communication circuit to draw less current from the energy storage capacitor.
 9. The load control device of claim 8, wherein the communication circuit comprises an RF communication circuit adapted to be coupled to an RF communication link.
 10. The load control device of claim 9, wherein the microprocessor is operable to cause the load control device to enter the low-power mode using an advanced programming mode of the load control device.
 11. The load control device of claim 9, wherein the microprocessor is operable to increase the sampling period of the RF communication circuit, such that the RF communication circuit wakes up less often to sample for RF energy.
 12. The load control device of claim 8, further comprising: a button for receiving a user input; wherein the microprocessor is operable to operate the load control device in a low-power mode in response to an actuation of the button.
 13. The load control device of claim 12, wherein the microprocessor is operable to cause the load control device to enter the low-power mode using an advanced programming mode of the load control device.
 14. The load control device of claim 8, wherein the load control device comprises a dimmer for controlling the power delivered to a lighting load.
 15. The load control device of claim 8, wherein the power supply comprises a transistor for controllably storing energy in the energy storage capacitor, the microprocessor operatively coupled to the transistor for controlling the transistor.
 16. The load control device of claim 8, wherein the microprocessor is operable to place the communication circuit in an idle mode when the load control device is in the low-power mode.
 17. A load control device for control of the power delivered from an AC power source to an electrical load, the load control device comprising: a controllably conductive device adapted to be coupled between the AC power source and the electrical load for controlling the power delivered to the load; a microprocessor coupled to the controllably conductive device for controlling the controllably conductive device; a power supply adapted to draw current from the AC power source through the electrical load for generating a DC voltage across an energy storage capacitor for powering the microprocessor; and a load circuit drawing current from the energy storage capacitor of the power supply; wherein the microprocessor is operable to cause the load circuit to draw less current if the magnitude of a voltage of the power supply drops below a predetermined threshold.
 18. The load control device of claim 17, wherein the load circuit comprises an LED controlled by the microprocessor to provide visual feedback.
 19. The load control device of claim 18, wherein the microprocessor is operable to turn off the LED in response to determining that the energy storage capacitor does not have enough time to charge during each half-cycle of the AC voltage.
 20. The load control device of claim 18, wherein the microprocessor is operable to dim the LED in response to determining that the energy storage capacitor does not have enough time to charge during each half-cycle of the AC voltage.
 21. The load control device of claim 18, wherein the load circuit comprises a plurality of LEDs controlled by the microprocessor to provide visual feedback; wherein the microprocessor is operable to cause the LEDs to draw less current in response to determining that the energy storage capacitor does not have enough time to sufficiently charge.
 22. The load control device of claim 17, wherein the load circuit comprises a communication circuit.
 23. The load control device of claim 22, wherein the communication circuit is adapted to be coupled to an RF communication link.
 24. The load control device of claim 23, wherein the microprocessor is operable to increase the sampling period of the RF communication circuit, such that the RF communication circuit wakes up less often to sample for RF energy.
 25. The load control device of claim 22, wherein the microprocessor is operable to place the communication circuit in an idle mode in response to determining that the energy storage capacitor does not have enough time to charge during each half-cycle of the AC voltage.
 26. The load control device of claim 17, wherein the load control device comprises a dimmer for controlling the power delivered to a lighting load. 